Multiple streams using partial stbc with sdm within a wireless local area network

ABSTRACT

A method of communicating data to M receiving antennas from N transmitting antennas, where M and N are integers, the method includes the steps of receiving M data signals from M receive antennas, applying the M data signals to a space/time decoder to produce M decoded streams and reconstructing original data transmitted via N transmit antennas from the M decoded streams. At least P transmitting antennas transmit space-time block-coded signals and (N-P) transmitting antennas transmit code signals through spatial division multiplexing, where P is an integer.

REFERENCE TO RELATED APPLICATIONS

This application claims priority of U.S. Provisional Patent ApplicationSer. No. 60/604,050, filed Aug. 25, 2004. The subject matter of thisearlier filed application is hereby incorporated by reference.

BACKGROUND OF THE INVENTION

1. Technical Field of the Invention

This invention relates generally to wireless communication systems andmore particularly to a transmitter transmitting at high data rates withsuch wireless communication systems. Additionally, the present inventionallows the detection and reception of multiple data streams for higherdata rates.

2. Description of Related Art

Communication systems support wireless and wire lined communicationsbetween wireless and/or wire lined communication devices. Suchcommunication systems range from national and/or international cellulartelephone systems to the Internet to point-to-point in-home wirelessnetworks. Each type of communication system is constructed, and henceoperates, in accordance with one or more communication standards. Forinstance, wireless communication systems may operate in accordance withone or more standards including, but not limited to, IEEE 802.11,BLUETOOTH™, advanced mobile phone services (AMPS), digital AMPS, globalsystem for mobile communications (GSM), code division multiple access(CDMA), local multi-point distribution systems (LMDS),multi-channel-multi-point distribution systems (MMDS), and/or variationsthereof.

For each wireless communication device to participate in wirelesscommunications, it may include a built-in radio transceiver (i.e.,receiver and transmitter) or may be coupled to an associated radiotransceiver (e.g., a station for in-home and/or in-building wirelesscommunication networks, RF modem, etc.). The transmitter may include adata modulation stage, one or more intermediate frequency stages, and apower amplifier. The data modulation stage converts raw data intobaseband signals in accordance with a particular wireless communicationstandard. The one or more intermediate frequency stages mix the basebandsignals with one or more local oscillations to produce RF signals. Thepower amplifier amplifies the RF signals prior to transmission via anantenna.

The transmitter may include a data modulation stage, one or moreintermediate frequency stages, and a power amplifier. The datamodulation stage can convert raw data into baseband signals inaccordance with a particular wireless communication standard. The one ormore intermediate frequency stages mix the baseband signals with one ormore local oscillations to produce RF signals. The power amplifieramplifies the RF signals prior to transmission via an antenna.

The transmitter includes at least one antenna for transmitting the RFsignals, which are received by a single antenna, or multiple antennas,of a receiver. When the receiver includes two or more antennas, thereceiver will select one of them to receive the incoming RF signals. Inthis instance, the wireless communication between the transmitter andreceiver is a single-output-single-input (SOSI) communication, even ifthe receiver includes multiple antennas that are used as diversityantennas (i.e., selecting one of them to receive the incoming RFsignals). For SISO wireless communications, a transceiver includes onetransmitter and one receiver.

Other types of wireless communications includesingle-input-multiple-output (SIMO), multiple-input-single-output(MISO), and multiple-input-multiple-output (MIMO). In a SIMO wirelesscommunication, a single transmitter processes data into radio frequencysignals that are transmitted to a receiver. The receiver includes two ormore antennas and two or more receiver paths. Each of the antennasreceives the RF signals and provides them to a corresponding receiverpath (e.g., LNA, down conversion module, filters, and ADCs). Each of thereceiver paths processes the received RF signals to produce digitalsignals, which are combined and then processed to recapture thetransmitted data.

For a multiple-input-single-output (MISO) wireless communication, thetransmitter includes two or more transmission paths (e.g., digital toanalog converter, filters, up-conversion module, and a power amplifier)that each converts a corresponding portion of baseband signals into RFsignals, which are transmitted via corresponding antennas to a receiver.The receiver includes a single receiver path that receives the multipleRF signals from the transmitter. In this instance, the receiver usesbeam forming to combine the multiple RF signals into one signal forprocessing.

For a multiple-input-multiple-output (MIMO) wireless communication, thetransmitter and receiver each include multiple paths. In such acommunication, the transmitter parallel processes data using a spatialand time encoding function to produce two or more streams of data. Thetransmitter includes multiple transmission paths to convert each streamof data into multiple RF signals. The receiver receives the multiple RFsignals via multiple receiver paths that recapture the streams of datautilizing a spatial and time decoding function. The recaptured streamsof data are combined and subsequently processed to recover the originaldata.

With the various types of wireless communications (e.g., SISO, MISO,SIMO, and MIMO), providing a diversity of transmitted signals isimportant to ensure proper data integrity. However, prior art systems donot have the ability to separate and detect signals from multiplestreams and realize the full benefits of those multiple streams.Therefore, a need exists for a receiver that has the ability to detectand separate signals from multiple streams so that coding and diversitygain may be realized.

BRIEF SUMMARY OF THE INVENTION

According to one embodiment of the present invention, a method ofcommunicating data to M receiving antennas from N transmitting antennas,where M and N are integers, the method includes the steps of receiving Mdata signals from M receive antennas, applying the M data signals to aspace/time decoder to produce M decoded streams and reconstructingoriginal data transmitted via N transmit antennas from the M decodedstreams. At least P transmitting antennas transmit space-timeblock-coded signals and (N-P) transmitting antennas transmit codesignals through spatial division multiplexing, where P is an integer.

Additionally, the step of reconstructing original data may includedetermining a number of transmit streams and configurations of thosetransmit streams through analysis of the M decoded streams. Also, P maybe two and the step of receiving M data signals includes receiving twospace-time block-coded signals. Also, when N is three, the step ofreceiving M data signals includes receiving a repetition code signal.Additionally, the step of reconstructing original data may includezero-forcing terms equivalent to relationships between signals sent fromthe N transmitting antennas to the M receiving antennas to cancelinterference.

According to another embodiment, a receiver for communicating data fromN transmitting antennas to M receiving antennas, where M and N areintegers, includes receiving means for receiving M data signals via Mreceive antennas, applying means for applying the M data signals to aspace/time decoder to produce M decoded streams and reconstructing meansfor reconstructing original data transmitted via N transmit antennasfrom the M decoded streams. At least P transmitting antennas transmitspace-time block-coded signals and (N-P) transmitting antennas transmitcode signals through spatial division multiplexing, where P is aninteger.

According to another embodiment, a receiver for communicating data fromN transmitting antennas to M receiving antennas, where M and N areintegers includes M receive antennas, for receiving M data signals, aspace/time decoder, configured to produce M decoded streams based on theM data signals and symbol demapping modules, configured to reconstructoriginal data transmitted via N transmit antennas from the M decodedstreams. At least P transmitting antennas transmit space-timeblock-coded signals and (N-P) transmitting antennas transmit codesignals through spatial division multiplexing, where P is an integer.

BRIEF DESCRIPTION OF THE DRAWINGS

For the present invention to be easily understood and readily practiced,the present invention will now be described, for purposes ofillustration and not limitation, in conjunction with the followingfigures:

FIG. 1 is a schematic block diagram of a wireless communication devicein accordance with one embodiment of the present invention;

FIG. 2 illustrates schematic block diagrams of a transmitter andreceiver, with FIG. 2( a) providing a schematic block diagram of an RFtransmitter and with FIG. 2( b) providing a schematic block diagram ofan RF receiver, in accordance with embodiments of the present invention;

FIGS. 3( a) and 3(b) are a schematic block diagram of a transmitter inaccordance one embodiment of with the present invention;

FIGS. 4( a) and 4(b) are a schematic block diagram of a receiver inaccordance with one embodiment of the present invention;

FIG. 5 is a diagram illustrating a Space-Time Block Coding (STBC) methodwith three transmit antennas to achieve one and a half streams, inaccordance with one embodiment of the present invention;

FIG. 6 is a diagram illustrating another STBC method with a SpatialDivision Multiplexing (SDM) component, with three transmit antennas toachieve two streams, in accordance with one embodiment of the presentinvention; and

FIG. 7 is a diagram illustrating another STBC method with SDMcomponents, with four transmit antennas to achieve three streams, inaccordance with one embodiment of the present invention.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS

FIG. 1 is a schematic block diagram illustrating a wirelesscommunication device, according to an example of the invention. Thedevice includes a baseband processing module 63, memory 65, a pluralityof radio frequency (RF) transmitters 67, 69, 71, a transmit/receive(T/R) module 73, a plurality of antennas 81, 83, 85, a plurality of RFreceivers 75, 77, 79, and a local oscillation module 99. The basebandprocessing module 63, in combination with operational instructionsstored in memory 65, execute digital receiver functions and digitaltransmitter functions, respectively. The digital receiver functionsinclude, but are not limited to, digital intermediate frequency tobaseband conversion, demodulation, constellation demapping, decoding,de-interleaving, fast Fourier transform, cyclic prefix removal, spaceand time decoding, and/or descrambling. The digital transmitterfunctions include, but are not limited to, scrambling, encoding,interleaving, constellation mapping, modulation, inverse fast Fouriertransform, cyclic prefix addition, space and time encoding, and/ordigital baseband to IF conversion. The baseband processing module 63 maybe implemented using one or more processing devices. Such a processingdevice may be a microprocessor, micro-controller, digital signalprocessor, microcomputer, central processing unit, field programmablegate array, programmable logic device, state machine, logic circuitry,analog circuitry, digital circuitry, and/or any device that manipulatessignals (analog and/or digital) based on operational instructions. Thememory 66 may be a single memory device or a plurality of memorydevices. Such a memory device may be a read-only memory, random accessmemory, volatile memory, non-volatile memory, static memory, dynamicmemory, flash memory, and/or any device that stores digital information.Note that when the processing module 63 implements one or more of itsfunctions via a state machine, analog circuitry, digital circuitry,and/or logic circuitry, the memory storing the corresponding operationalinstructions is embedded with the circuitry comprising the statemachine, analog circuitry, digital circuitry, and/or logic circuitry.

In operation, the baseband processing module 63 receives the outbounddata 87 and, based on a mode selection signal 101, produces one or moreoutbound symbol streams 89. The mode selection signal 101 will indicatea particular mode as are indicated in mode selection tables. Forexample, the mode selection signal 101 may indicate a frequency band of2.4 GHz, a channel bandwidth of 20 or 22 MHz and a maximum bit rate of54 megabits-per-second. In this general category, the mode selectionsignal will further indicate a particular rate ranging from 1megabit-per-second to 54 megabits-per-second. In addition, the modeselection signal will indicate a particular type of modulation, whichincludes, but is not limited to, Barker Code Modulation, BPSK, QPSK,CCK, 16 QAM and/or 64 QAM. A code rate is supplied as well as number ofcoded bits per subcarrier (NBPSC), coded bits per OFDM symbol (NCBPS),data bits per OFDM symbol (NDBPS), error vector magnitude in decibels(EVM), sensitivity which indicates the maximum receive power required toobtain a target packet error rate (e.g., 10% for IEEE 802.11a), adjacentchannel rejection (ACR), and an alternate adjacent channel rejection(AACR).

The mode selection signal may also indicate a particular channelizationfor the corresponding mode. The mode select signal may further indicatea power spectral density mask value. The mode select signal mayalternatively indicate a rate that has a 5 GHz frequency band, 20 MHzchannel bandwidth and a maximum bit rate of 54 megabits-per-second. As afurther alternative, the mode select signal 101 may indicate a 2.4 GHzfrequency band, 20 MHz channels and a maximum bit rate of 192megabits-per-second. A number of antennas may be utilized to achieve thehigher bandwidths. In this instance, the mode select would furtherindicate the number of antennas to be utilized. Another mode option maybe utilized where the frequency band is 2.4 GHz, the channel bandwidthis 20 MHz and the maximum bit rate is 192 megabits-per-second. Variousbit rates ranging from 12 megabits-per-second to 216 megabits-per-secondutilizing 2-4 antennas and a spatial time encoding rate may be employed.The mode select signal 101 may further indicate a particular operatingmode, which corresponds to a 5 GHz frequency band having 40 MHzfrequency band having 40 MHz channels and a maximum bit rate of 486megabits-per-second. The bit rate may range, in this example, from 13.5megabits-per-second to 486 megabits-per-second utilizing 1-4 antennasand a corresponding spatial time code rate.

The baseband processing module 63, based on the mode selection signal101 produces the one or more outbound symbol streams 89 from the outputdata 88. For example, if the mode selection signal 101 indicates that asingle transmit antenna is being utilized for the particular mode thathas been selected, the baseband processing module 63 will produce asingle outbound symbol stream 89. Alternatively, if the mode selectsignal indicates 2, 3 or 4 antennas, the baseband processing module 63will produce 2, 3 or 4 outbound symbol streams 89 corresponding to thenumber of antennas from the output data 88.

Depending on the number of outbound streams 89 produced by the basebandmodule 63, a corresponding number of the RF transmitters 67, 69, 71 canbe enabled to convert the outbound symbol streams 89 into outbound RFsignals 91. The implementation of the RF transmitters 67, 69, 71 will befurther described with reference to FIG. 2. The transmit/receive module73 receives the outbound RP signals 91 and provides each outbound RFsignal to a corresponding antenna 81, 83, 85.

When the radio 60 is in the receive mode, the transmit/receive module 73receives one or more inbound RF signals via the antennas 81, 83, 85. TheT/R module 73 provides the inbound RF signals 93 to one or more RFreceivers 75, 77, 79. The RF receiver 75, 77, 79, which will bedescribed in greater detail with reference to FIG. 4, converts theinbound RF signals 93 into a corresponding number of inbound symbolstreams 96. The number of inbound symbol streams 95 will correspond tothe particular mode in which the data was received. The basebandprocessing module 63 receives the inbound symbol streams 89 and convertsthem into inbound data 97.

As one of average skill in the art will appreciate, the wirelesscommunication device of FIG. 1 may be implemented using one or moreintegrated circuits. For example, the device may be implemented on oneintegrated circuit, the baseband processing module 63 and memory 65 maybe implemented on a second integrated circuit, and the remainingcomponents, less the antennas 81, 83, 85, may be implemented on a thirdintegrated circuit. As an alternate example, the device may beimplemented on a single integrated circuit.

FIG. 2( a) is a schematic block diagram of an embodiment of an RFtransmitter 67, 69, 71. The RF transmitter may include a digital filterand up-sampling module 475, a digital-to-analog conversion module 477,an analog filter 479, and up-conversion module 81, a power amplifier 483and a RF filter 485. The digital filter and up-sampling module 475receives one of the outbound symbol streams 89 and digitally filters itand then up-samples the rate of the symbol streams to a desired rate toproduce the filtered symbol streams 487. The digital-to-analogconversion module 477 converts the filtered symbols 487 into analogsignals 489. The analog signals may include an in-phase component and aquadrature component.

The analog filter 479 filters the analog signals 489 to produce filteredanalog signals 491. The up-conversion module 481, which may include apair of mixers and a filter, mixes the filtered analog signals 491 witha local oscillation 493, which is produced by local oscillation module99, to produce high frequency signals 495. The frequency of the highfrequency signals 495 corresponds to the frequency of the RF signals492.

The power amplifier 483 amplifies the high frequency signals 495 toproduce amplified high frequency signals 497. The RF filter 485, whichmay be a high frequency band-pass filter, filters the amplified highfrequency signals 497 to produce the desired output RF signals 91.

As one of average skill in the art will appreciate, each of the radiofrequency transmitters 67, 69, 71 will include a similar architecture asillustrated in FIG. 2( a) and further include a shut-down mechanism suchthat when the particular radio frequency transmitter is not required, itis disabled in such a manner that it does not produce interferingsignals and/or noise.

FIG. 2( b) is a schematic block diagram of each of the RF receivers 75,77, 79. In this embodiment, each of the RF receivers may include an RFfilter 501, a low noise amplifier (LNA) 503, a programmable gainamplifier (PGA) 505, a down-conversion module 507, an analog filter 509,an analog-to-digital conversion module 511 and a digital filter anddown-sampling module 513. The RF filter 501, which may be a highfrequency band-pass filter, receives the inbound RF signals 93 andfilters them to produce filtered inbound RF signals. The low noiseamplifier 503 amplifies the filtered inbound RF signals 93 based on again setting and provides the amplified signals to the programmable gainamplifier 505. The programmable gain amplifier further amplifies theinbound RF signals 93 before providing them to the down-conversionmodule 507.

The down-conversion module 507 includes a pair of mixers, a summationmodule, and a filter to mix the inbound RF signals with a localoscillation (LO) that is provided by the local oscillation module toproduce analog baseband signals. The analog filter 509 filters theanalog baseband signals and provides them to the analog-to-digitalconversion module 511 which converts them into a digital signal. Thedigital filter and down-sampling module 513 filters the digital signalsand then adjusts the sampling rate to produce the inbound symbol stream95.

FIGS. 3( a) and 3(b) illustrate a schematic block diagram of a multipletransmitter in accordance with the present invention. In FIG. 3( a), thebaseband processing is shown to include a scrambler 172, channel encoder174, interleaver 176, demultiplexer 170, a plurality of symbol mappers180-1 through 180-m, a space/time encoder 190 and a plurality of inversefast Fourier transform (IFFT)/cyclic prefix addition modules 192-1through 192-m. The baseband portion of the transmitter may furtherinclude a mode manager module 175 that receives the mode selectionsignal and produces settings for the radio transmitter portion andproduces the rate selection for the baseband portion.

In operations, the scrambler 172 adds (in GF2) a pseudo random sequenceto the outbound data bits 88 to make the data appear random. A pseudorandom sequence may be generated from a feedback shift register with thegenerator polynomial, for example, of S(x)=x⁷+x⁴+1 to produce scrambleddata. The channel encoder 174 receives the scrambled data and generatesa new sequence of bits with redundancy. This will enable improveddetection at the receiver. The channel encoder 174 may operate in one ofa plurality of modes. For example, for backward compatibility withstandards such as IEEE 802.11(a) and IEEE 802.11(g), the channel encoderhas the form of a rate ½ convolutional encoder with 64 states and agenerator polynomials of G₀=133₈ and G₁=171₈. The output of theconvolutional encoder may be punctured to rates of ½, ⅔rds and ¾according to the specified rate tables. For backward compatibility withIEEE 802.11(b) and the CCK modes of IEEE 802.11(g), the channel encoderhas the form of a CCK code as defined in IEEE 802.11(b). For higher datarates, the channel encoder may use the same convolution encoding asdescribed above or it may use a more powerful code, including aconvolutional code with more states, a parallel concatenated (turbo)code and/or a low density parity check (LDPC) block code. Further, anyone of these codes may be combined with an outer Reed Solomon code.Based on a balancing of performance, backward compatibility and lowlatency, one or more of these codes may be optimal.

The interleaver 176 receives the encoded data and spreads it overmultiple symbols and transmit streams. This allows improved detectionand error correction capabilities at the receiver. In one embodiment,the interleaver 176 will follow the IEEE 802.11(a) or (g) standard inthe backward compatible modes. For higher performance modes, theinterleaver will interleave data over multiple transmit streams. Thedemultiplexer 170 converts the serial interleave stream from interleaver176 into M-parallel streams for transmission.

Each symbol mapper 180-m through 180-m receives a corresponding one ofthe M-parallel paths of data from the demultiplexer. Each symbol mapperlocks maps bit streams to quadrature amplitude modulated QAM symbols(e.g., BPSK, QPSK, 16 QAM, 64 QAM, 256 QAM, et cetera) according to therate tables. For IEEE 802.11 (a) backward compatibility, double graycoding may be used.

The map symbols produced by each of the symbol mappers 180 are providedto the space/time encoder 190. Thereafter, output symbols are providedto the IFFT/cyclic prefix addition modules 192-1 through 192-m, whichperforms frequency domain to time domain conversions and adds a prefix,which allows removal of inter-symbol interference at the receiver. Ingeneral, a 64-point IFFT will be used for 20 MHz channels and 128-pointIFFT will be used for 40 MHz channels.

In one embodiment, the number of M-input paths will equal the number ofP-output paths. In another embodiment, the number of output paths P willequal M+1 paths. For each of the paths, the space/time encoder multiplesthe input symbols with an encoding matrix that has the form of:

$\quad\begin{bmatrix}C_{1} & C_{2} & C_{3} & \ldots & C_{2\; M} \\{- C_{2}^{\star}} & C_{1}^{\star} & {- C_{4}^{\star}} & \ldots & C_{({{2M} - 1})}^{\star}\end{bmatrix}$

Note that the rows of the encoding matrix correspond to the number ofinput paths and the columns correspond to the number of output paths.

FIG. 3( b) illustrates the radio portion of the transmitter thatincludes a plurality of digital filter/up-sampling modules 195-1 through195-m, digital-to-analog conversion modules 200-1 through 200-m, analogfilters 210-1 through 210-m and 215-1 through 215-m, I/Q modulators220-1 through 220-m, RF amplifiers 225-1 through 225-m, RF filters 230-1through 230-m and antennas 240-1 through 240-m. The P-outputs from theother stage are received by respective digital filtering/up-samplingmodules 195-1 through 195-m.

In operation, the number of radio paths that are active correspond tothe number of P-outputs. For example, if only one P-output path isgenerated, only one of the radio transmitter paths will be active. Asone of average skill in the art will appreciate, the number of outputpaths may range from one to any desired number.

The digital filtering/up-sampling modules 195-1 through 195-m filter thecorresponding symbols and adjust the sampling rates to correspond withthe desired sampling rates of the digital-to-analog conversion modules200. The digital-to-analog conversion modules 200 convert the digitalfiltered and up-sampled signals into corresponding in-phase andquadrature analog signals. The analog filters 210 and 215 filter thecorresponding in-phase and/or quadrature components of the analogsignals, and provide the filtered signals to the corresponding I/Qmodulators 220. The I/Q modulators 220 based on a local oscillation,which is produced by a local oscillator 100, up-converts the I/Q signalsinto radio frequency signals. The RF amplifiers 225 amplify the RFsignals which are then subsequently filtered via RF filters 230 beforebeing transmitted via antennas 240.

FIGS. 4( a) and 4(b) illustrate a schematic block diagram of anotherembodiment of a receiver in accordance with the present invention. FIG.4( a) illustrates the analog portion of the receiver which includes aplurality of receiver paths. Each receiver path includes an antenna250-1 through 250-n, RF filters 255-1 through 255-n, low noiseamplifiers 260-1 through 260-n, I/O demodulators 265-1 through 265-n,analog filters 270-1 through 270-n and 275-1 through 275-n,analog-to-digital converters 280-1 through 280-n and digital filters anddown-sampling modules 290-1 through 290-n.

In operation, the antennas 250 receive inbound RF signals, which areband-pass filtered via the RF filters 255. The corresponding low noiseamplifiers 260 amplify the filtered signals and provide them to thecorresponding I/Q demodulators 265. The I/Q demodulators 265, based on alocal oscillation, which is produced by local oscillator 100,down-converts the RF signals into baseband in-phase and quadratureanalog signals.

The corresponding analog filters 270 and 275 filter the in-phase andquadrature analog components, respectively. The analog-to-digitalconverters 280 convert the in-phase and quadrature analog signals into adigital signal. The digital filtering and down-sampling modules 290filter the digital signals and adjust the sampling rate to correspond tothe rate of the baseband processing, which will be described in FIG. 4(b).

FIG. 4( b) illustrates the baseband processing of a receiver. Thebaseband processing portion includes a plurality of fast Fouriertransform (FFT)/cyclic prefix removal modules 294-1 through 294-n, aspace/time decoder 296, a plurality of symbol demapping modules 300-1through 300-n, a multiplexer 310, a deinterleaver 312, a channel decoder314, and a descramble module 316. The baseband processing module mayfurther include a mode managing module 175. The receiver paths areprocessed via the FFT/cyclic prefix removal modules 294 which performthe inverse function of the IFFT/cyclic prefix addition modules 192 toproduce frequency domain symbols as M-output paths. The space/timedecoding module 296, which performs the inverse function of space/timeencoder 190, receives the M-output paths.

The symbol demapping modules 300 convert the frequency domain symbolsinto data utilizing an inverse process of the symbol mappers 180. Themultiplexer 310 combines the demapped symbol streams into a single path.

The deinterleaver 312 deinterleaves the single path utilizing an inversefunction of the function performed by interleaver 176. The deinterleaveddata is then provided to the channel decoder 314 which performs theinverse function of channel encoder 174. The descrambler 316 receivesthe decoded data and performs the inverse function of scrambler 172 toproduce the inbound data 98.

As noted above, STBC is usually performed with pairs of antennas,utilizing Orthogonal Frequency Division Multiplexing (OFDM). Withmultiple antennas, i.e. with more than two antennas, multiple streamscan be utilized to achieve higher data rates. In such cases, STBC isapplied over some of the transmit antennas, but other antennas transmitsignals without STBC. These other antennas may transmit using SpatialDivision Multiplexing (SDM). Thus, portions of the signal streams havediversity gains, while others do not. In this way, it is also possibleto have greater coding gains from better signal streams. Given theseadditional possibilities, a receiver according to the present inventionshould have the ability to detect and separate signals to achieve thesegains.

FIG. 5 is a basic diagram illustrating one embodiment of STBCrealization or transmission with SDM by the receiver 521. Multiplesignals, c₁(t), c₂(t) and c₃(t), are received from an encoding block.The t_(i) denotes an encoding interval index in time, usually a twosymbol period for the STBC encoder. After coding, c₁ and c₂ aretransmitted through transmission antennas 510 a and 510 b, and signal c₃is transmitted through transmission antenna 515 a. The signals c₁ and c₂can be configured with conjugate values and signal c₃ is encoded byrepetition coding. The transmitted signals are received by the STBCdecoding block 521, through receive antennas 520 a and 520 b. Afterprocessing, signals, c₁, c₂, and c₃, based on the originally transmittedsignals are reformulated and output through outputs 551, 552 and 553. Ingeneral, the received signals are related to the source signals throughan “H” or “G” component plus a noise term.

From this set-up, the channels may be estimated as:

$\begin{matrix}{{\begin{bmatrix}r_{1} \\r_{2}\end{bmatrix}_{4 \times 1} = {{\begin{bmatrix}H_{1} & G_{1} \\H_{2} & G_{2}\end{bmatrix}_{4 \times 3}\begin{bmatrix}c_{1} \\c_{2}\end{bmatrix}}_{3 \times 1} + \begin{bmatrix}n_{1} \\n_{2}\end{bmatrix}_{4 \times 1}}}{{where},{c_{1} = \begin{bmatrix}{c_{1}\left( t_{0} \right)} \\{c_{2}\left( t_{0} \right)}\end{bmatrix}},{c_{2} = \left\lbrack {c_{3}\left( t_{0} \right)} \right\rbrack},{r_{1} = \begin{bmatrix}{r_{1}\left( t_{0} \right)} \\{r_{1}^{\star}\left( t_{1} \right)}\end{bmatrix}},{r_{2} = \begin{bmatrix}{r_{2}\left( t_{0} \right)} \\{r_{2}^{\star}\left( t_{1} \right)}\end{bmatrix}},{H_{i} = \begin{bmatrix}h_{1i} & h_{2\; i} \\h_{2\; i}^{\star} & {- h_{1i}^{\star}}\end{bmatrix}},{G_{i} = \begin{bmatrix}g_{i} \\g_{i}^{\star}\end{bmatrix}}}} & (1)\end{matrix}$

To cancel the interference, zero forcing is applied such that:

$\begin{matrix}{{{\begin{bmatrix}\begin{bmatrix}1 & 0 \\0 & 1\end{bmatrix} & \begin{bmatrix}{{- g_{1}}g_{2}^{- 1}} & 0 \\0 & {{- g_{1}} \star g_{2}^{- 1^{\star}}}\end{bmatrix} \\{\mspace{11mu} {z_{1}\mspace{20mu} z_{2}}} & {z_{3} z_{4}}\end{bmatrix}_{3 \times 4} \times \left\lbrack \begin{matrix}r_{1} \\r_{2}\end{matrix} \right\rbrack} = {\left\lbrack \begin{matrix}{\overset{\sim}{r}}_{1} \\{\overset{\sim}{r}}_{2}\end{matrix} \right\rbrack = {{\begin{bmatrix}\overset{\sim}{H} & 0 \\0 & \overset{\sim}{G}\end{bmatrix}_{3 \times 3} \times \begin{bmatrix}c_{1} \\c_{2}\end{bmatrix}} + \begin{bmatrix}{\overset{\sim}{n}}_{1} \\{\overset{\sim}{n}}_{2}\end{bmatrix}}}}{{where},{{\overset{\sim}{H}}_{2 \times 2} = {H_{1} - {\begin{bmatrix}{{- g_{1}}g_{2}^{- 1}} & 0 \\0 & {{- g_{1}} \star g_{2}^{- 1^{\star}}}\end{bmatrix} \times H_{2}}}},{{\overset{\sim}{G}}_{1 \times 1} = \sqrt{{g_{1}}^{2} + {g_{2}}^{2}}},}} & (2)\end{matrix}$

and z₁, z₂, z₃ and z₄ satisfy the following equation:

h ₁₁ z ₁ +h ₂₁ *z ₂ +h ₁₂ z ₃ +h ₂₂ *z ₄=0

h ₂₁ z ₁ −h ₁₁ *z ₂ +h ₂₂ z ₃ −h ₁₂ *z ₄=0

g ₁ z ₁ +g ₁ *z ₂ +g ₂ z ₃ +g ₂ *z ₄=√{square root over (|g ₁|² +|g₂|²)}  (3)

Thereafter Z is found by zero-forcing to minimize noise enhancement,such that:

$\begin{matrix}{z = {\left( {AA}^{\star} \right)^{- 1}A^{\star}c}} & (4) \\{{where},{z = \begin{bmatrix}z_{1} & z_{2} & z_{3} & z_{4}\end{bmatrix}^{\prime}},{A = \begin{bmatrix}h_{11} & h_{21}^{\star} & h_{12} & h_{22}^{\star} \\h_{22} & {- h_{11}^{\star}} & h_{22} & {- h_{12}^{\star}} \\g_{1} & g_{1}^{\star} & g_{2} & g_{2}^{\star}\end{bmatrix}},{c = {\begin{bmatrix}0 & 0 & \sqrt{{g_{1}}^{2} + {g_{2}}^{2}}\end{bmatrix}^{\prime}.}}} & \;\end{matrix}$

Next, STBC decoding may be performed with channel matching such that

$\begin{matrix}{{{\begin{bmatrix}{\overset{\sim}{H}}^{\star} & \; & 0 \\\; & \; & 0 \\0 & 0 & {\overset{\sim}{G}}^{\star}\end{bmatrix}\begin{bmatrix}{\overset{\sim}{r}}_{1} \\{\overset{\sim}{r}}_{2}\end{bmatrix}} = {{\begin{bmatrix}{{\overset{\sim}{H}}^{\star}\overset{\sim}{H}} & \; & 0 \\\; & \; & 0 \\0 & 0 & {{\overset{\sim}{G}}^{\star}\overset{\sim}{G}}\end{bmatrix}\begin{bmatrix}c_{1} \\c_{2}\end{bmatrix}} + \begin{bmatrix}N_{1} \\N_{2}\end{bmatrix}}}\mspace{11mu} {{where},{{{\overset{\sim}{H}}^{\star}\overset{\sim}{H}} = {\left( {H_{1} - {\begin{bmatrix}{{- g_{1}}g_{2}^{- 1}} & 0 \\0 & {{- g_{1}} \star g_{2}^{- 1^{\star}}}\end{bmatrix} \times H_{2}}} \right)^{\star}\left( {H_{1} - {\begin{bmatrix}{{- g_{1}}g_{2}^{- 1}} & 0 \\0 & {{- g_{1}} \star g_{2}^{- 1^{\star}}}\end{bmatrix} \times H_{2}}} \right)}},\mspace{56mu} \; {{{\overset{\sim}{G}}^{\star}\overset{\sim}{G}} = {{g_{1}}^{2} + {g_{2}}^{2}}},}} & (5)\end{matrix}$

which is diagonalized and constant x identity.

FIG. 6 is a basic diagram illustrating another embodiment of STBCrealization or transmission with SDM by the receiver 621. Multiplesignals, c₁(t), c₂(t), c₃(t) and c₄(t), are received from an encodingblock. After coding, c₁ and c₂ are transmitted through transmissionantennas 610 a and 610 b, and signals c₃ and c₄ are transmitted throughtransmission antenna 615 a. The signals c₁ and c₂ can be configured withconjugate values and signals c₃ and c₄ are being transmitted as in SDMwith conjugate. The transmitted signals are received by the STBCdecoding block 621, through receive antennas 620 a and 620 b. Afterprocessing, signals, c₁, c₂, c₃ and c₄, based on the originallytransmitted signals are reformulated and output through outputs 651-654.In general, the received signals are related to the source signalsthrough an “H” or “G” component plus a noise term.

From this set-up, the channels may be estimated as:

$\begin{matrix}{{\begin{bmatrix}r_{1} \\r_{2}\end{bmatrix}_{4 \times 1} = {{\begin{bmatrix}H_{1} & G_{1} \\H_{2} & G_{2}\end{bmatrix}_{4 \times 4}\begin{bmatrix}c_{1} \\c_{2}\end{bmatrix}}_{4 \times 1} + \begin{bmatrix}n_{1} \\n_{2}\end{bmatrix}_{4 \times 1}}}\; {{where},{c_{1} = \begin{bmatrix}{c_{1}\left( t_{0} \right)} \\{c_{2}\left( t_{0} \right)}\end{bmatrix}},{c_{2} = \begin{bmatrix}{c_{3}\left( t_{0} \right)} \\{c_{4}\left( t_{0} \right)}\end{bmatrix}},{r_{1} = \begin{bmatrix}{r_{1}\left( t_{0} \right)} \\{r_{1}^{\star}\left( t_{1} \right)}\end{bmatrix}},{r_{2} = \begin{bmatrix}{r_{2}\left( t_{0} \right)} \\{r_{2}^{\star}\left( t_{1} \right)}\end{bmatrix}},{H_{i} = \begin{bmatrix}h_{1i} & h_{2\; i} \\h_{2\; i}^{\star} & {- h_{1i}^{\star}}\end{bmatrix}},{G_{i} = \left\lbrack {\begin{matrix}g_{i} \\0\end{matrix}\begin{matrix}0 \\g_{i}^{\star}\end{matrix}} \right\rbrack}}} & (6)\end{matrix}$

To cancel the interference, zero forcing is applied such that:

$\begin{matrix}{{\begin{bmatrix}\begin{bmatrix}1 & 0 \\0 & 1\end{bmatrix} & \begin{bmatrix}{{- g_{1}}g_{2}^{- 1}} & 0 \\0 & {{- g_{1}} \star g_{2}^{- 1^{\star}}}\end{bmatrix} \\{\mspace{11mu} {z_{11}\mspace{20mu} z_{12}}} & {z_{13}\mspace{14mu} z_{14}} \\{\mspace{11mu} {z_{21\mspace{25mu}}z_{22}}} & {z_{23\mspace{14mu}}z_{24}}\end{bmatrix} \times \begin{bmatrix}r_{1} \\r_{2}\end{bmatrix}} = {\quad{{\begin{bmatrix}{\overset{\sim}{r}}_{1} \\{\overset{\sim}{r}}_{2}\end{bmatrix} = {{\begin{bmatrix}\overset{\sim}{H} & 0 \\0 & \overset{\sim}{G}\end{bmatrix}_{4 \times 4} \times \begin{bmatrix}c_{1} \\c_{2}\end{bmatrix}} + {\begin{bmatrix}{\overset{\sim}{n}}_{1} \\{\overset{\sim}{n}}_{2}\end{bmatrix}{where}}}},{{\overset{\sim}{H}}_{2 \times 2} = {H_{1} - {\begin{bmatrix}{{- g_{1}}g_{2}^{- 1}} & 0 \\0 & {{- g_{1}} \star g_{2}^{- 1^{\star}}}\end{bmatrix} \times H_{2}}}},{{\overset{\sim}{G}}_{2 \times 2} = {\sqrt{{g_{1}}^{2} + {g_{2}}^{2}} \times \begin{bmatrix}1 & 0 \\0 & 1\end{bmatrix}}},}\mspace{59mu}}} & (7)\end{matrix}$

and z_(ij) satisfy the following equation:

h ₁₁ z _(i1) +h ₂₁ *z _(i2) +h ₁₂ z _(i3) +h ₂₂ *z _(i4)=0

h ₂₁ z _(i1) −h ₁₁ *z _(i2) +h ₂₂ z _(i3) −h ₁₂ *z _(i4)=0

g ₁ z ₁₁ +g ₂ z ₁₃=√{square root over (|g ₁|² +|g ₂|²)}

g ₁ *z ₂₂ +g ₂ *z ₂₄=√{square root over (|g ₁|² +|g ₂|²)}  (8)

with i being 1 or 2 in the above series of equations.

Thereafter Z is found by zero-forcing to minimize noise enhancement,such that:

$\begin{matrix}{{z = {\left( {AA}^{*} \right)^{- 1}A^{*}c}}{{z = \begin{bmatrix}z_{11} & z_{12} & z_{13} & z_{14} \\z_{21} & z_{22} & z_{23} & z_{24}\end{bmatrix}^{\prime}},{A = \begin{bmatrix}h_{11} & h_{21}^{*} & h_{12} & h_{22}^{*} \\h_{21} & {- h_{11}^{*}} & h_{22} & {- h_{12}^{*}} \\g_{1} & 0 & g_{2} & 0 \\0 & g_{1}^{*} & 0 & g_{2}^{*}\end{bmatrix}},{where},{c = \begin{bmatrix}0 & 0 & \sqrt{{g_{1}}^{2} + {g_{2}}^{2}} & 0 \\0 & 0 & 0 & \sqrt{{g_{1}}^{2} + {g_{2}}^{2}}\end{bmatrix}^{\prime}}}} & (9)\end{matrix}$

Next, STBC decoding may be performed with channel matching such that

$\begin{matrix}{{{\begin{bmatrix}{\overset{\sim}{H}}^{*} & 0 \\0 & {\overset{\sim}{G}}^{*}\end{bmatrix}\begin{bmatrix}{\overset{\sim}{r}}_{1} \\{\overset{\sim}{r}}_{2}\end{bmatrix}} = {{\begin{bmatrix}{{\overset{\sim}{H}}^{*}\overset{\sim}{H}} & \begin{matrix}0 \\0\end{matrix} \\{0\mspace{25mu} 0} & {{\overset{\sim}{G}}^{*}\overset{\sim}{G}}\end{bmatrix}\begin{bmatrix}c_{1} \\c_{2}\end{bmatrix}} + \begin{bmatrix}N_{1} \\N_{2}\end{bmatrix}}}{{{{\overset{\sim}{H}}^{*}\overset{\sim}{H}} = {\left( {H_{1} - {\begin{bmatrix}{{- g_{1}}g_{2}^{- 1}} & 0 \\0 & {{- g_{1}^{*}}g_{2}^{{- 1}*}}\end{bmatrix} \times H_{2}}} \right)^{*}\left( {H_{1} - {\begin{bmatrix}{{- g_{1}}g_{2}^{- 1}} & 0 \\0 & {{- g_{1}^{*}}g_{2}^{{- 1}*}}\end{bmatrix} \times H_{2}}} \right)}},{where},{{{\overset{\sim}{G}}^{*}\overset{\sim}{G}} = {\left( {{g_{1}}^{2} + {g_{2}}^{2}} \right) \times \begin{bmatrix}1 & 0 \\0 & 1\end{bmatrix}}},}} & (10)\end{matrix}$

which is diagonalized and constant x identity.

FIG. 7 is a basic diagram illustrating another embodiment of STBCrealization or transmission with SDM by the receiver 721. Multiplesignals, c₁(t), c₂(t), c₃(t), c₄(t), c₅(t) and c₆(t), are received froman encoding block. After coding, c₁ and c₂ are transmitted throughtransmission antennas 710 a and 710 b, and signals c₃, c₄, c₅ and c₆ aretransmitted through transmission antennas 715 a and 715 b. The signalsc₁ and c₂ can be configured with conjugate values and signals c₃, c₄, c₅and c₆ are being transmitted as in SDM with conjugates. The transmittedsignals are received by the STBC decoding, block 721, through receiveantennas 720 a, 720 b and 720 c. After processing, signals, c₁ and c₂,based on the originally transmitted signals are reformulated and outputthrough outputs 751 and 752. In general, the received signals arerelated to the source signals through an “H” or “G” component plus anoise term.

From this set-up, the channels may be estimated as:

$\begin{matrix}{{\begin{bmatrix}r_{1} \\r_{2} \\r_{3}\end{bmatrix}_{6 \times 1} = {{\begin{bmatrix}H_{1} & G_{1} \\H_{2} & G_{2} \\H_{3} & G_{3}\end{bmatrix}_{6 \times 6}\begin{bmatrix}c_{1} \\c_{2} \\c_{3}\end{bmatrix}}_{6 \times 1} + \begin{bmatrix}n_{1} \\n_{2} \\n_{3}\end{bmatrix}_{6 \times 1}}}{where},{c_{1} = \begin{bmatrix}{c_{1}\left( t_{0} \right)} \\{c_{2}\left( t_{0} \right)}\end{bmatrix}},{c_{2} = \begin{bmatrix}{c_{3}\left( t_{0} \right)} \\{c_{4}\left( t_{0} \right)}\end{bmatrix}},{c_{3} = \begin{bmatrix}{c_{5}\left( t_{0} \right)} \\{c_{6}\left( t_{0} \right)}\end{bmatrix}},{r_{1} = \begin{bmatrix}{r_{1}\left( t_{0} \right)} \\{r_{1}^{*}\left( t_{1} \right)}\end{bmatrix}},{r_{2} = \begin{bmatrix}{r_{2}\left( t_{0} \right)} \\{r_{2}^{*}\left( t_{1} \right)}\end{bmatrix}},{r_{3} = \begin{bmatrix}{r_{3}\left( t_{0} \right)} \\{r_{3}^{*}\left( t_{1} \right)}\end{bmatrix}},{H_{i} = \begin{bmatrix}h_{1i} & h_{2i} \\h_{2i}^{*} & {- h_{1i}^{*}}\end{bmatrix}},{G_{i} = \begin{bmatrix}g_{1i} & 0 & g_{2i} & 0 \\0 & g_{1i}^{*} & 0 & g_{2i}^{*}\end{bmatrix}}} & (11)\end{matrix}$

To cancel the interference, zero forcing is applied such that:

$\begin{matrix}{\quad{{\begin{bmatrix}\; & \begin{bmatrix}1 & 0 \\0 & 1\end{bmatrix} & \; & \; & \begin{bmatrix}a_{1} & 0 & a_{2} & 0 \\0 & a_{1}^{*} & 0 & a_{2}^{*}\end{bmatrix} & \; \\z_{11} & z_{12} & z_{13} & z_{14} & z_{15} & z_{16} \\z_{21} & z_{22} & z_{23} & z_{24} & z_{25} & z_{26} \\z_{31} & z_{32} & z_{33} & z_{34} & z_{35} & z_{36} \\z_{41} & z_{42} & z_{43} & z_{44} & z_{45} & z_{46}\end{bmatrix} \times \begin{bmatrix}r_{1} \\r_{2} \\r_{3}\end{bmatrix}} = {\quad{{\begin{bmatrix}{\overset{\sim}{r}}_{1} \\{\overset{\sim}{r}}_{2} \\{\overset{\sim}{r}}_{3}\end{bmatrix} = {{\begin{bmatrix}\overset{\sim}{H} & 0 \\0 & \overset{\sim}{G}\end{bmatrix}_{6 \times 6} \times \begin{bmatrix}c_{1} \\c_{2} \\c_{3}\end{bmatrix}} + {\begin{bmatrix}{\overset{\sim}{n}}_{1} \\{\overset{\sim}{n}}_{2} \\{\overset{\sim}{n}}_{3}\end{bmatrix}{where}}}},\text{}{{\overset{\sim}{H}}_{2 \times 2} = {H_{1} - {\begin{bmatrix}a_{1} & 0 & a_{2} & 0 \\0 & a_{1}^{*} & 0 & a_{2}^{*}\end{bmatrix} \times \begin{bmatrix}H_{2} \\H_{3}\end{bmatrix}}}},{{\overset{\sim}{G}}_{4 \times 4} = \begin{bmatrix}{\sqrt{\sum\limits_{i = 1}^{3}{g_{1\; i}}^{2}} \times I_{2 \times 2}} & 0 \\0 & {\sqrt{\sum\limits_{i = 1}^{3}{g_{2\; i}}^{2}} \times I_{2 \times 2}}\end{bmatrix}},}}}} & (12)\end{matrix}$

Thereafter Z is found by zero-forcing to minimize noise enhancement,such that:

z=(AA*)⁻¹ A*c  (13)

where,

${z = \left\lbrack z_{ij} \right\rbrack^{\prime}},{c = \begin{bmatrix}0_{2 \times 4} & {\overset{\sim}{G}}_{4 \times 4}\end{bmatrix}^{\prime}},{A = \begin{bmatrix}H_{1} & G_{1} \\H_{2} & G_{2} \\H_{3} & G_{3}\end{bmatrix}^{\prime}}$

and a₁ and a₂ are also found by zero forcing

$\begin{bmatrix}a_{1} \\a_{2}\end{bmatrix} = {\begin{bmatrix}g_{12} & g_{13} \\g_{22} & g_{23}\end{bmatrix}^{- 1} \times {\begin{bmatrix}{- g_{11}} \\{- g_{21}}\end{bmatrix}.}}$

Next, STBC decoding may be performed with channel matching in processessimilar to those discussed in the above-discussed embodiments. In all ofthe above discussed embodiments, at least a pair of transmit antennasare used for STBC (c₁(t₀) and c₂(t₀)), the other transmit antennas maytransmit SDM signals. Thus, while only the first two sequences, c₁(t)and c₂(t), will obtain diversity gain, but there may be additionalcoding gains based on good quality bits. The additional sequencesprovide signal-to-noise advantages using repetition codes.

Although the invention has been described based upon these preferredembodiments, it would be apparent to those skilled in the art thatcertain modifications, variations, and alternative constructions wouldbe apparent, while remaining within the spirit and scope of theinvention. In order to determine the metes and bounds of the invention,therefore, reference should be made to the appended claims.

1-24. (canceled)
 25. A method of communicating data to M receivingantennas from N transmitting antennas, where M and N are integers, themethod comprising: receiving M data signals from M receive antennas;applying the M data signals to a space block decoder to produce Mdecoded streams; and reconstructing original data transmitted via Ntransmit antennas from the M decoded streams; wherein at least Ptransmitting antennas of the N transmitting antennas transmit spaceblock-coded signals and (N-P) transmitting antennas of the Ntransmitting antennas transmit code signals through spatial divisionmultiplexing, where P is an integer.
 26. The method of claim 25, whereinthe reconstructing of original data comprises determining a number oftransmit streams and configurations of those transmit streams throughanalysis of the M decoded streams.
 27. The method of claim 25, wherein Pcomprises two and the receiving of M data signals comprises receivingtwo space block-coded signals.
 28. The method of claim 27, wherein Ncomprises three and the receiving of M data signals comprises receivinga repetition code signal.
 29. A method according to claim 25, whereinthe reconstructing of original data comprises zero-forcing termsequivalent to relationships between signals sent from the N transmittingantennas to the M receiving antennas to cancel interference.
 30. Amethod according to claim 29, wherein the relationships comprise:$\begin{bmatrix}r_{1} \\r_{2}\end{bmatrix} = {{\begin{bmatrix}H_{1} & G_{1} \\H_{2} & G_{2}\end{bmatrix}\begin{bmatrix}c_{1} \\c_{2}\end{bmatrix}} + \begin{bmatrix}n_{1} \\n_{2}\end{bmatrix}}$ ${where},{c_{1} = \begin{bmatrix}{c_{1}\left( t_{0} \right)} \\{c_{2}\left( t_{1} \right)}\end{bmatrix}},{c_{2} = \left\lbrack {c_{2}\left( t_{0} \right)} \right\rbrack},{r_{1} = \begin{bmatrix}{r_{1}\left( t_{1} \right)} \\{r_{1}^{*}\left( t_{2} \right)}\end{bmatrix}},{r_{2} = \begin{bmatrix}{r_{2}\left( t_{1} \right)} \\{r_{2}^{*}\left( t_{2} \right)}\end{bmatrix}},{H_{i} = \begin{bmatrix}h_{1\; i} & h_{2i} \\h_{2i}^{*} & {- h_{1i}^{*}}\end{bmatrix}},{G_{i} = \begin{bmatrix}g_{i} \\g_{i}^{*}\end{bmatrix}},$ where r_(i)(t) and c_(i)(t) are the received andtransmitted signals, respectively, n_(i) represent noise terms and G_(i)and H_(i) represent relationships between signals sent from threetransmit antennas to two receive antennas.
 31. A method according toclaim 29, wherein the relationships comprise: $\begin{bmatrix}r_{1} \\r_{2}\end{bmatrix}_{4 \times 1} = {{\begin{bmatrix}H_{1} & G_{1} \\H_{2} & G_{2}\end{bmatrix}_{4 \times 4}\begin{bmatrix}c_{1} \\c_{2}\end{bmatrix}}_{4 \times 1} + \begin{bmatrix}n_{1} \\n_{2}\end{bmatrix}_{4 \times 1}}$ ${where},{c_{1} = \begin{bmatrix}{c_{1}\left( t_{0} \right)} \\{c_{2}\left( t_{0} \right)}\end{bmatrix}},{c_{2} = \begin{bmatrix}{c_{3}\left( t_{0} \right)} \\{c_{4}\left( t_{0} \right)}\end{bmatrix}},{r_{1} = \begin{bmatrix}{r_{1}\left( t_{0} \right)} \\{r_{1}^{*}\left( t_{1} \right)}\end{bmatrix}},{r_{2} = \begin{bmatrix}{r_{2}\left( t_{0} \right)} \\{r_{2}^{*}\left( t_{1} \right)}\end{bmatrix}},{H_{i} = \begin{bmatrix}h_{1i} & h_{2i} \\h_{2i}^{*} & {- h_{1i}^{*}}\end{bmatrix}},{G_{i} = \begin{bmatrix}g_{i} & 0 \\0 & g_{i}^{*}\end{bmatrix}}$ where r_(i)(t) and c_(i)(t) are the received andtransmitted signals, respectively, n_(i) represent noise terms and G_(i)and H_(i) represent relationships between signals sent three transmitantennas to two receive antennas.
 32. A method according to claim 29,wherein the relationships comprise: $\begin{bmatrix}r_{1} \\r_{2} \\r_{3}\end{bmatrix}_{6 \times 1} = {{\begin{bmatrix}H_{1} & G_{1} \\H_{2} & G_{2} \\H_{3} & G_{3}\end{bmatrix}_{6 \times 6}\begin{bmatrix}c_{1} \\c_{2} \\c_{3}\end{bmatrix}}_{6 \times 1} + \begin{bmatrix}n_{1} \\n_{2} \\n_{3}\end{bmatrix}_{6 \times 1}}$ ${where},{c_{1} = \begin{bmatrix}{c_{1}\left( t_{0} \right)} \\{c_{2}\left( t_{0} \right)}\end{bmatrix}},{c_{2} = \begin{bmatrix}{c_{3}\left( t_{0} \right)} \\{c_{4}\left( t_{0} \right)}\end{bmatrix}},{c_{3} = \begin{bmatrix}{c_{5}\left( t_{0} \right)} \\{c_{6}\left( t_{0} \right)}\end{bmatrix}},{r_{1} = \begin{bmatrix}{r_{1}\left( t_{0} \right)} \\{r_{1}^{*}\left( t_{1} \right)}\end{bmatrix}},{r_{2} = \begin{bmatrix}{r_{2}\left( t_{0} \right)} \\{r_{2}^{*}\left( t_{1} \right)}\end{bmatrix}},{r_{3} = \begin{bmatrix}{r_{3}\left( t_{0} \right)} \\{r_{3}^{*}\left( t_{1} \right)}\end{bmatrix}},{H_{i} = \begin{bmatrix}h_{1i} & h_{2i} \\h_{2i}^{*} & {- h_{1i}^{*}}\end{bmatrix}},{G_{i} = \begin{bmatrix}g_{1i} & 0 & g_{2i} & 0 \\0 & g_{1i}^{*} & 0 & g_{2i}^{*}\end{bmatrix}}$ where r_(i)(t) and c_(i)(t) are the received andtransmitted signals, respectively, n_(i) represent noise terms and G_(i)and H_(i) represent relationships between signals sent from fourtransmit antennas to three receive antennas.
 33. A receiver forcommunicating data from N transmitting antennas to M receiving antennas,where M and N are integers, comprising: a space block decoder,configured to produce M decoded streams based on M data signals receivedvia M receive antennas; and symbol demapping modules, configured toreconstruct original data transmitted via N transmit antennas from the Mdecoded streams; wherein at least P transmitting antennas of the Ntransmitting antennas transmit space block-coded signals and (N-P)transmitting antennas of the N transmitting antennas transmit codesignals through spatial division multiplexing, where P is an integer.34. The receiver of claim 33, wherein the space block decoder isconfigured to determine a number of transmit streams and configurationsof those transmit streams through analysis of the M decoded streams. 35.The receiver of claim 33, wherein P comprises two and the space blockdecoder is configured to receive two space block-coded signals.
 36. Thereceiver of claim 35, wherein N comprises three and the space blockdecoder is configured to receive a repetition code signal.
 37. Areceiver according to claim 33, wherein the space block decoder isconfigured to zero-force terms equivalent to relationships betweensignals sent from the N transmitting antennas to the M receivingantennas to cancel interference.
 38. A receiver according to claim 37,wherein the relationships comprise: $\begin{bmatrix}r_{1} \\r_{2}\end{bmatrix} = {{\begin{bmatrix}H_{1} & G_{1} \\H_{2} & G_{2}\end{bmatrix}\begin{bmatrix}c_{1} \\c_{2}\end{bmatrix}} + \begin{bmatrix}n_{1} \\n_{2}\end{bmatrix}}$ ${where},{c_{1} = \begin{bmatrix}{c_{1}\left( t_{0} \right)} \\{c_{1}\left( t_{1} \right)}\end{bmatrix}},{c_{2} = \left\lbrack {c_{2}\left( t_{0} \right)} \right\rbrack},{r_{1} = \begin{bmatrix}{r_{1}\left( t_{1} \right)} \\{r_{1}^{*}\left( t_{2} \right)}\end{bmatrix}},{r_{2} = \begin{bmatrix}{r_{2}\left( t_{1} \right)} \\{r_{2}^{*}\left( t_{2} \right)}\end{bmatrix}},{H_{i} = \begin{bmatrix}h_{1i} & h_{2i} \\h_{2i}^{*} & {- h_{1i}^{*}}\end{bmatrix}},{G_{i} = \begin{bmatrix}g_{i} \\g_{i}^{*}\end{bmatrix}},$ where r_(i)(t) and c_(i)(t) are the received andtransmitted signals, respectively, n_(i) represent noise terms and G_(i)and H_(i) represent relationships between signals sent from threetransmit antennas to two receive antennas.
 39. A receiver according toclaim 37, wherein the relationships comprise: $\begin{bmatrix}r_{1} \\r_{2}\end{bmatrix}_{4 \times 1} = {{\begin{bmatrix}H_{1} & G_{1} \\H_{2} & G_{2}\end{bmatrix}_{4 \times 4}\begin{bmatrix}c_{1} \\c_{2}\end{bmatrix}}_{4 \times 1} + \begin{bmatrix}n_{1} \\n_{2}\end{bmatrix}_{4 \times 1}}$ ${where},{c_{1} = \begin{bmatrix}{c_{1}\left( t_{0} \right)} \\{c_{2}\left( t_{0} \right)}\end{bmatrix}},{c_{2} = \begin{bmatrix}{c_{3}\left( t_{0} \right)} \\{c_{4}\left( t_{0} \right)}\end{bmatrix}},{r_{1} = \begin{bmatrix}{r_{1}\left( t_{0} \right)} \\{r_{1}^{*}\left( t_{1} \right)}\end{bmatrix}},{r_{2} = \begin{bmatrix}{r_{2}\left( t_{0} \right)} \\{r_{2}^{*}\left( t_{1} \right)}\end{bmatrix}},{H_{i} = \begin{bmatrix}h_{1i} & h_{2i} \\h_{2i}^{*} & {- h_{1i}^{*}}\end{bmatrix}},{G_{i} = \begin{bmatrix}g_{i} & 0 \\0 & g_{i}^{*}\end{bmatrix}}$ where r_(i)(t) and c_(i)(t) are the received andtransmitted signals, respectively, n_(i) represent noise terms and G_(i)and H_(i) represent relationships between signals sent three transmitantennas to two receive antennas.
 40. A receiver according to claim 37,wherein the relationships comprise: $\begin{bmatrix}r_{1} \\r_{2} \\r_{3}\end{bmatrix}_{6 \times 1} = {{\begin{bmatrix}H_{1} & G_{1} \\H_{2} & G_{2} \\H_{3} & G_{3}\end{bmatrix}_{6 \times 6}\begin{bmatrix}c_{1} \\c_{2} \\c_{3}\end{bmatrix}}_{6 \times 1} + \begin{bmatrix}n_{1} \\n_{2} \\n_{3}\end{bmatrix}_{6 \times 1}}$ ${where},{c_{1} = \begin{bmatrix}{c_{1}\left( t_{0} \right)} \\{c_{2}\left( t_{0} \right)}\end{bmatrix}},{c_{2} = \begin{bmatrix}{c_{3}\left( t_{0} \right)} \\{c_{4}\left( t_{0} \right)}\end{bmatrix}},{c_{3} = \begin{bmatrix}{c_{5}\left( t_{0} \right)} \\{c_{6}\left( t_{0} \right)}\end{bmatrix}},{r_{1} = \begin{bmatrix}{r_{1}\left( t_{0} \right)} \\{r_{1}^{*}\left( t_{1} \right)}\end{bmatrix}},{r_{2} = \begin{bmatrix}{r_{2}\left( t_{0} \right)} \\{r_{2}^{*}\left( t_{1} \right)}\end{bmatrix}},{r_{3} = \begin{bmatrix}{r_{3}\left( t_{0} \right)} \\{r_{3}^{*}\left( t_{1} \right)}\end{bmatrix}},{H_{i} = \begin{bmatrix}h_{1i} & h_{2i} \\h_{2i}^{*} & {- h_{1i}^{*}}\end{bmatrix}},{G_{i} = \begin{bmatrix}g_{1i} & 0 & g_{2i} & 0 \\0 & g_{1i}^{*} & 0 & g_{2i}^{*}\end{bmatrix}}$ where r_(i)(t) and c_(i)(t) are the received andtransmitted signals, respectively, n_(i) represent noise terms and G_(i)and H_(i) represent relationships between signals sent from fourtransmit antennas to three receive antennas.
 41. A receiver forcommunicating data from N transmitting antennas to M receiving antennas,where M and N are integers, comprising: M receive antennas, forreceiving M data signals; a space block decoder, configured to produce Mdecoded streams based on the M data signals; and symbol demappingmodules, configured to reconstruct original data transmitted via Ntransmit antennas from the M decoded streams; wherein at least Ptransmitting antennas of the N transmitting antennas transmit spaceblock-coded signals and (N-P) transmitting antennas of the Ntransmitting antennas transmit code signals through spatial divisionmultiplexing, where P is an integer.
 42. The receiver of claim 41,wherein the space block decoder is configured to determine a number oftransmit streams and configurations of those transmit streams throughanalysis of the M decoded streams.
 43. The receiver of claim 41, whereinP comprises two and the space block decoder is configured to receive twospace block-coded signals.
 44. The receiver of claim 43, wherein Ncomprises three and the space block decoder is configured to receive arepetition code signal.
 45. A receiver according to claim 41, whereinthe space block decoder is configured to zero-force terms equivalent torelationships between signals sent from the N transmitting antennas tothe M receiving antennas to cancel interference.
 46. A receiveraccording to claim 45, wherein the relationships comprise:$\begin{bmatrix}r_{1} \\r_{2}\end{bmatrix} = {{\begin{bmatrix}H_{1} & G_{1} \\H_{2} & G_{2}\end{bmatrix}\begin{bmatrix}c_{1} \\c_{2}\end{bmatrix}} + \begin{bmatrix}n_{1} \\n_{2}\end{bmatrix}}$ ${where},{c_{1} = \begin{bmatrix}{c_{1}\left( t_{0} \right)} \\{c_{1}\left( t_{1} \right)}\end{bmatrix}},{c_{2} = \left\lbrack {c_{2}\left( t_{0} \right)} \right\rbrack},{r_{1} = \begin{bmatrix}{r_{1}\left( t_{1} \right)} \\{r_{1}^{*}\left( t_{2} \right)}\end{bmatrix}},{r_{2} = \begin{bmatrix}{r_{2}\left( t_{1} \right)} \\{r_{2}^{*}\left( t_{2} \right)}\end{bmatrix}},{H_{i} = \begin{bmatrix}h_{1i} & h_{2i} \\h_{2i}^{*} & {- h_{1i}^{*}}\end{bmatrix}},{G_{i} = \begin{bmatrix}g_{i} \\g_{i}^{*}\end{bmatrix}},$ where r_(i)(t) and c_(i)(t) are the received andtransmitted signals, respectively, n_(i) represent noise terms and G_(i)and H_(i) represent relationships between signals sent from threetransmit antennas to two receive antennas.
 47. A receiver according toclaim 45, wherein the relationships comprise: $\begin{bmatrix}r_{1} \\r_{2}\end{bmatrix}_{4 \times 1} = {{\begin{bmatrix}H_{1} & G_{1} \\H_{2} & G_{2}\end{bmatrix}_{4 \times 4}\begin{bmatrix}c_{1} \\c_{2}\end{bmatrix}}_{4 \times 1} + \begin{bmatrix}n_{1} \\n_{2}\end{bmatrix}_{4 \times 1}}$ ${where},{c_{1} = \begin{bmatrix}{c_{1}\left( t_{0} \right)} \\{c_{2}\left( t_{0} \right)}\end{bmatrix}},{c_{2} = \begin{bmatrix}{c_{3}\left( t_{0} \right)} \\{c_{4}\left( t_{0} \right)}\end{bmatrix}},{r_{1} = \begin{bmatrix}{r_{1}\left( t_{0} \right)} \\{r_{1}^{*}\left( t_{1} \right)}\end{bmatrix}},{r_{2} = \begin{bmatrix}{r_{2}\left( t_{0} \right)} \\{r_{2}^{*}\left( t_{1} \right)}\end{bmatrix}},{H_{i} = \begin{bmatrix}h_{1i} & h_{2i} \\h_{2i}^{*} & {- h_{1i}^{*}}\end{bmatrix}},{G_{i} = \begin{bmatrix}g_{i} & 0 \\0 & g_{i}^{*}\end{bmatrix}}$ where r_(i)(t) and c_(i)(t) are the received andtransmitted signals, respectively, n_(i) represent noise terms and G_(i)and H_(i) represent relationships between signals sent three transmitantennas to two receive antennas.
 48. A receiver according to claim 45,wherein the relationships comprise: $\begin{bmatrix}r_{1} \\r_{2} \\r_{3}\end{bmatrix}_{6 \times 1} = {{\begin{bmatrix}H_{1} & G_{1} \\H_{2} & G_{2} \\H_{3} & G_{3}\end{bmatrix}_{6 \times 6}\begin{bmatrix}c_{1} \\c_{2} \\c_{3}\end{bmatrix}}_{6 \times 1} + \begin{bmatrix}n_{1} \\n_{2} \\n_{3}\end{bmatrix}_{6 \times 1}}$ ${where},{c_{1} = \begin{bmatrix}{c_{1}\left( t_{0} \right)} \\{c_{2}\left( t_{0} \right)}\end{bmatrix}},{c_{2} = \begin{bmatrix}{c_{3}\left( t_{0} \right)} \\{c_{4}\left( t_{0} \right)}\end{bmatrix}},{c_{3} = \begin{bmatrix}{c_{5}\left( t_{0} \right)} \\{c_{6}\left( t_{0} \right)}\end{bmatrix}},{r_{1} = \begin{bmatrix}{r_{1}\left( t_{0} \right)} \\{r_{1}^{*}\left( t_{1} \right)}\end{bmatrix}},{r_{2} = \begin{bmatrix}{r_{2}\left( t_{0} \right)} \\{r_{2}^{*}\left( t_{1} \right)}\end{bmatrix}},{r_{3} = \begin{bmatrix}{r_{3}\left( t_{0} \right)} \\{r_{3}^{*}\left( t_{1} \right)}\end{bmatrix}},{H_{i} = \begin{bmatrix}h_{1i} & h_{2i} \\h_{2i}^{*} & {- h_{1i}^{*}}\end{bmatrix}},{G_{i} = \begin{bmatrix}g_{1i} & 0 & g_{2i} & 0 \\0 & g_{1i}^{*} & 0 & g_{2i}^{*}\end{bmatrix}}$ where r_(i)(t) and c_(i)(t) are the received andtransmitted signals, respectively, n_(i) represent noise terms and G_(i)and H_(i) represent relationships between signals sent from fourtransmit antennas to three receive antennas.